Skip to main content

A 100-Mhz Bandwidth 80-dB Dynamic Range Continuous-Time Delta-Sigma Modulator with a 2.4-Ghz Clock Rate


The bandwidth of a ΔΣ modulator is limited by the clock rate due to the oversampling ratio requirement. As the nanoscale CMOS processes are developing rapidly, it is possible to design wide bandwidth and high dynamic range continuous-time ΔΣ modulators for high-frequency applications. This paper proposes a 3rd-order 4-bit continuous-time ΔΣ modulator with a single-loop feedforward topology. This modulator is designed in a 40-nm CMOS process and achieves 80-dB dynamic range and a 100-MHz bandwidth at a clock rate of 2.4 GHz. The modulator consumes 69.7 mW from 1.2 V power supply.


Driven by the increasing demands in wireless communication applications such as cellular standards, analog-to-digital converters (ADCs) evolve rapidly to support higher signal bandwidth (BW) and dynamic range (DR). The requirement of BW in Long-Term-Evolution Advanced (LTE-A) communication standard has risen to 100 MHz. Nyquist ADCs, typically pipeline ADCs [1, 2], have been used in macro base stations for their high BW. However, indispensable input buffers for driving thermal-noise-limited switched input capacitors and anti-aliasing filter cause significant power consumption and design complexity. Furthermore, the fact that pipeline ADCs rely on accurate inter-stage gain, which determines high-gain wideband residue amplifier and calibration technology, leads to complexity and power dissipation. ΔΣ ADCs are known for their high performance and power efficiency employing oversampling and noise shaping technology. However, the requirement of oversampling ratios (OSRs), which is typically over 16 [36], determines sampling frequency beyond GHz. Recently, ΔΣ ADCs exceeding 50 MHz BW have been proposed by using nanoscale CMOS processes, which allow multi-GHz clock rate. Previously, high frequency ΔΣ ADCs usually adopt continuous-time (CT) realizations [39] instead of discrete-time (DT) realizations. The latter is implemented by switched capacitor circuit, and its accuracy relies on capacitor matching, which means a robust operation under process variation is offered. Besides, superior immunity to clock jitter is provided since the time constants of the capacitors and switches are sufficiently small. However, as the sampling operation executes before modulator, the anti-aliasing filter is needed. On the other hand, due to the settling requirement to ensure stability in the stages, operational amplifiers in DT modulators are implemented with broader unity-gain bandwidth (UGBW) than CT modulators. In summary, DT modulators can provide high accuracy but narrow signal [10, 11] and are widely used to implement metering applications such as smart sensors and biomedical imaging. In contrast, there has been more widespread effort to design CT modulators for high frequency applications than DT ones with comparable complexity and power consumption.

The demanding design target of higher BW in a given process determines a lower OSR because of process-limited clock rate. To achieve a sufficient DR, an aggressive noise shaping implemented by high noise transfer function order, which is conventionally performed by loop filter cascade and generally equal or greater than 3 in previous works, is required. However, the increased loop filter orders cause power consumption, instability, and design complexity. The multi-stage noise-shaping (MASH) architecture [6, 8], implemented by cascaded low-order local ΔΣ modulators without feedback path among each other, was employed to alleviate stability issues but with mismatch sensitiveness. Moreover, a modulator with a multi-bits quantizer gets a conditionally high DR with an exponential increasing comparator amount.

This paper describes a CT modulator in 40 nm CMOS that achieves 80 DR over 100 MHz BW with 69.7 mW consumption using 40 nm CMOS process. This paper is organized as follows. The “Method” section describes the modulator topology and circuit implementation. The “Results and Discussion” section shows simulated results, and the “Conclusion” section provides a summary of this work.


Figure 1 illustrates the overall schematic of the proposed 3rd-order CT ΔΣ modulator with the single-ended structure for simplification. The 3rd-order noise shaping gets a great compromise between the DR and the loop stability. The proposed modulator has a sampling rate of 2.4 GHz with a 12 OSR. The relatively high OSR in ΔΣ modulators exceeded 100 MHz BW ensures a high DR. The modulator contains three RC integrators, a 4-bit quantizer and a 4-bit current-steering DAC. The integrators are implemented by innovational low-power dissipation feedforward amplifiers for high energy efficiency. The feedback DAC has a half sampling period duration extra delay to relax the metastability requirement of the quantizer. A fast feedback path implemented by a passive adder and driven directly by quantizer realizes the excess-loop-delay (ELD) compensation. A feedforward topology is employed for power efficiency at the expense of out-of-band signal-transfer-function.

Fig. 1

Overall schematic of proposed single-loop 3rd-order 4-bit CT ΔΣ modulator with a feedforward topology

Amplifier Design

High amplifier gain is required in ΔΣ modulators to ensure the desired noise transform function. However, the nanoscale technologies used to achieve multi-GHz clock rate suffer in low intrinsic gain. Therefore, a three-stage amplifier is adopted to implement sufficient DC gain, as shown in Fig. 2. Feedforward topology and Miller compensation are combined to improve phase margin without unit gain bandwidth reduction. Feedforward amplifiers have been one popular solution of achieving high gain with adequate UGBW and phase margin (PM). The left-half plane zero caused by the feed-forward path is supposed to effectively cancel the negative phase shift of poles. It requires high transconductance of the amplifiers on the feed-forward path and consumes significant power. The advantaged scheme of re-using bias current saves power whereas it limits gm values. Insufficient gm typically causes the zero beyond the UGBW and cannot provide an adequate phase margin. An optimized zero located below the overall UGBW is provided by adding a Miller compensating capacitor and a nulling resistor.

Fig. 2

Topology of the proposed three-stage feedforward amplifier with Miller compensation

Figure 3 shows the transistor-level schematic of the amplifier used in the first integrator. Transistors M1−4 form the input stage of amplifier, while transistors M9,10 and M13,14 form the second and third stage, respectively. Transistors M5−8 and M11,12 create two high-speed feedforward paths between the input and output while sharing bias currents with the second- and third-stage amplifiers. The first-stage output common-mode (CM) is fixed locally. The second-stage and the 3rd-stage output CM is fixed by a second-stage feedback path across a CMFB amplifier, M7,8 and M13,14. Figure 4 a shows the simulated post-layout open-loop response of amplifier of the first integrator with all loading while Fig. 4 b shows the close-loop response. The first integrator achieves 3.6 GHz of UGBW and 57.8 of PM with all loading effect while consumes 10.5 mW from a 1.2-V supply. The second and third integrators adopt the same topology but with scaled bias currents, achieving UGBW of 4.7 and 3.3 GHz and PM of 58.0 and 57.8 while consuming 4.3 and 17.3 mW, respectively.

Fig. 3

Amplifier transistor-level schematic

Fig. 4

The post-layout simulated results of the amplifier in the 1st integrator. a Open-loop ac response; b Close-loop ac response

Quantizer and DAC

As the schematic of the quantizer and DAC shown in Fig. 5, each consists of 16 unit cells. The quantizer is realized as a 4-bit flash ADCs with 16-level encoder generated from a 17-tap resistive ladder. The quantizer, whose operation duration is demanded by ELD to less than half a sampling period to ensure loop stability, is a key block as a limitation of maximum BW.

Fig. 5

The simplified schematic of the quantizers and the DACs

To implement high-speed flash ADCs, a three-stage comparator architecture consisting of a preamplifier stage, a dynamic comparator stage, and a symmetric set-and-reset (SR) latch[12], illustrated as Fig. 6, is employed. The preamplifier for input-referred offset reduction is two resistively load differential pairs with a reset switch connecting across outputs to enable quick recovery. Unlike conventional dynamic comparators, the differential pair and cross-coupled inverters are split into two parts to minimize the amount of transistor in every current path for low-voltage supplies. When the clock turns to the high level, dynamic comparators start to make the input-dependent comparison decision. Then, the two outputs of each dynamic comparator are both reset to 0 as the clock return goes from high to low, triggering the regeneration and latching of the symmetric SR latch. Since only one transistor in each branch is active, the symmetric SR latch structure leads a strong loading driving capability. It allows a small transistor size with significant switch off speed and low power consumption. Furthermore, it results in equal delays of both output signals. The D latches before DAC units are low-level-sensitive with respect to the level of the clock signal, ensuring a half ELD duration. The transistor-level circuit of the current steering DAC unit is shown in Fig. 7.

Fig. 6

Transistor-level circuit of one unit element of the proposed quantizer

Fig. 7

The PMOS current steering DAC unit element

Results and Discussion

The prototype ΔΣ modulator is built in a 40-nm CMOS process. As the post-simulated results of the SNR and SDNR vs. input amplitude at 10.2 MHz shown in Fig. 8, a 80-dB DR is achieved. Figures 9 and 10 show the simulated spectra with a − 3.52-dBF single-tone input at 10.2 MHz and 97 MHz, respectively, since 0 dBF corresponds to the 2.4 Vpp modulator full scale. The SNDR is 77.47 dB and 76.53 dB, respectively. As the breakdown consumption shown in Fig. 11, the modulator costs 69.7 mW power consumption. The integrator, the quantizer, and the DAC respectively consume 32.1 mW, 25.4 mW, and 6.2 mW. 6.0 mW power is consumed by the other currents including clock buffers, current biases, and the voltage references. The modulator achieves a Schreier FOM of 171.6 dB based on DR. Table 1 compares this work with several previously published works. The proposed modulator achieves wide BW with the highest FOM.

Fig. 8

Post-simulated SNR and SNDR vs. input signal amplitude with a 10.2-MHz input

Fig. 9

The post-simulated spectra with a single-tone input at 10.2 MHz

Fig. 10

The post-simulated spectra with a single-tone input at 97 MHz

Fig. 11

The post-simulated power consumption breakdown

Table 1 Comparison of this work with the recent state-of-the-art ΔΣ modulator


In this work, we proposed a 3rd-order 4-bit CT ΔΣ modulator with a single-loop feedforward topology. This modulator is designed in a 40-nm CMOS process and achieves 80 dB DR over a 100-MHz BW at a clock rate of 2.4 GHz. The low-power dissipation amplifier construction leads a high-energy efficiency, and the modulator consumes 69.7 mw from 1.2 V power supply and achieves a Schreier FOM of 171.6 dB.

Availability of Data and Materials

All data generated or analyzed during this study are included in this published article.



Analog-to-digital converters






Dynamic range






Long-Term-Evolution Advanced


Oversampling ratios


Phase margin


Unity-gain bandwidth


  1. 1

    Ali AMA, Dinc H, Bhoraskar P, Dillon C, Puckett S, Gray B, Speir C, Lanford J, Brunsilius J, Derounian PR, Jeffries B, Mehta U, McShea M, Stop R (2014) A 14 bit 1 GS/s RF sampling pipelined ADC with background calibration. IEEE J Solid State Circ 49(12):2857–2867.

    Article  Google Scholar 

  2. 2

    Ali AMA, Dillon C, Sneed R, Morgan AS, Bardsley S, Kornblum J, Wu L (2006) A 14-bit 125 MS/s IF/RF sampling pipelined ADC with 100 dB SFDR and 50 fs jitter. IEEE J Solid State Circ 41(8):1846–1855.

    Article  Google Scholar 

  3. 3

    Bolatkale M, Breems LJ, Rutten R, Makinwa KAA (2011) A 4 GHz continuous-time ΔΣ ADC with 70 dB DR and −74 dBFS THD in 125 MHz BW. IEEE J Solid State Circ 46(12):2857–2868.

    Article  Google Scholar 

  4. 4

    Caldwell T, Alldred D, Li Z (2014) A reconfigurable ΔΣ ADC with up to 100 MHz bandwidth using flash reference shuffling. IEEE Trans Circ Syst I Regular Paper 61(8):2263–2271.

    Article  Google Scholar 

  5. 5

    Srinivasan V, Wang V, Satarzadeh P, Haroun B, Corsi M (2012) A 20mW 61dB SNDR (60MHz BW) 1b 3rd-order continuous-time delta-sigma modulator clocked at 6GHz in 45nm CMOS In: 2012 IEEE International Solid-State Circuits Conference, 158–160.

  6. 6

    Yoon D, Ho S, Lee H (2015) A continuous-time sturdy-MASH ΔΣ modulator in 28 nm CMOS. IEEE J Solid State Circ 50(12):2880–2890.

    Article  Google Scholar 

  7. 7

    Wu S, Kao T, Lee Z, Chen P, Tsai J (2016) A 160MHz-BW 72dB-DR 40mW continuous-time ΔΣ modulator in 16nm CMOS with analog ISI-reduction technique In: 2016 IEEE International Solid-State Circuits Conference (ISSCC), 280–281.

  8. 8

    Dong Y, Zhao J, Yang WW, Caldwell T, Shibata H, Li Z, Schreier R, Meng Q, Silva JB, Paterson D, Gealow JC (2016) A 72 dB-DR 465 MHz-BW continuous-time 1-2 MASH ADC in 28 nm CMOS. IEEE J Solid State Circ 51(12):2917–2927.

    Article  Google Scholar 

  9. 9

    Ho S, Lo C, Ru J, Zhao J (2015) A 23 mW, 73 dB dynamic range, 80 MHz BW continuous-time delta-sigma modulator in 20 nm CMOS. IEEE J Solid State Circ 50(4):908–919.

    Article  Google Scholar 

  10. 10

    Karmakar S, Gònen B, Sebastiano F, Van Veldhoven R, Makinwa KAA (2018) A 280 μW dynamic-zoom ADC with 120dB DR and 118dB SNDR in 1kHz BW In: 2018 IEEE International Solid - State Circuits Conference - (ISSCC), 238–240.

  11. 11

    Steiner M, Greer N (2016) 15.8 A 22.3b 1kHz 12.7mW switched-capacitor ΔΣ modulator with stacked split-steering amplifiers In: 2016 IEEE International Solid-State Circuits Conference (ISSCC), 284–286.

  12. 12

    Nikolic B, Oklobdzija VG, Stojanovic V, Wenyan J, Chiu JK-S, Leung M-TM (2000) Improved sense-amplifier-based flip-flop: design and measurements. IEEE J Solid State Circ 35(6):876–884.

    Article  Google Scholar 

Download references


Not applicable.


This work was supported in part by Department of Science and Technology of Sichuan Province under Grant 2018GZDZX0001, 2018GZDZX0002, and 2018GZ0080.

Author information




YX designed the circuit, verified the circuit with simulation, and was a major contributor in writing the manuscript. HT provided the ideas and directed the design procedure. The rest of the authors offered comments and revised the manuscript. All authors read and approved the final manuscript.

Corresponding author

Correspondence to He Tang.

Ethics declarations

Competing Interests

The authors declare that they have no competing interests.

Additional information

Publisher’s Note

Springer Nature remains neutral with regard to jurisdictional claims in published maps and institutional affiliations.

Rights and permissions

Open Access This article is licensed under a Creative Commons Attribution 4.0 International License, which permits use, sharing, adaptation, distribution and reproduction in any medium or format, as long as you give appropriate credit to the original author(s) and the source, provide a link to the Creative Commons licence, and indicate if changes were made. The images or other third party material in this article are included in the article’s Creative Commons licence, unless indicated otherwise in a credit line to the material. If material is not included in the article’s Creative Commons licence and your intended use is not permitted by statutory regulation or exceeds the permitted use, you will need to obtain permission directly from the copyright holder. To view a copy of this licence, visit

Reprints and Permissions

About this article

Verify currency and authenticity via CrossMark

Cite this article

Xiao, Y., Lu, Z., Ren, Z. et al. A 100-Mhz Bandwidth 80-dB Dynamic Range Continuous-Time Delta-Sigma Modulator with a 2.4-Ghz Clock Rate. Nanoscale Res Lett 15, 58 (2020).

Download citation


  • Delta-sigma modulator
  • Wide-bandwidth
  • Nanoscale CMOS process
  • Continuous-time